Self-synchronising bit error analyser and circuit

ABSTRACT

A self-synchronising data bus analyser comprising a generator LFSR, a receiver LFSR and a comparator
     wherein the generator LFSR generates a first data set which is transmitted through a data bus to the comparator; and   wherein the comparator compares the first data set with a second data set generated by the receiver LFSR and adjusts the receiver LFSR until the second data set is substantially the same as the first data set.

TECHNICAL FIELD

The present invention relates to a self-synchronising bit error analyser and circuit therefor device capable of determining the bit error rate of single data rate (SDR) and double data rate (DDR) data.

BACKGROUND

The present invention provides a mechanism of assessing the performance of high-speed data buses. Accordingly, it is useful at this point to briefly review such data buses and the techniques that are currently used for assessing their performance. These topics will be discussed with reference to the accompanying Figures in which:

FIG. 1 is a block diagram of a typical receiver in a hybrid parallel-serial interface; and

FIG. 2 is a block diagram of a typical bit error testing device.

Modern software products (such as streaming video/audio etc.) have contributed to the ever-increasing demand for higher bandwidth data buses. High-speed data buses such as PCI-express, Hype Transport and RapidIO are replacing the traditional parallel PCI bus with a point-to-point communications system in which addressing information is packaged together with data and the resulting packets are transmitted over serial transmission lines. More recently, hybrid parallel-serial interfaces have been developed in which data is transmitted over multiple serial transmission lines operating in parallel.

Referring to FIG. 1, a receiver 10 in a hybrid parallel-serial interface typically comprises a differential I/O buffer 12, a clock and data recovery (CDR) circuit 14, a deserialiser or rate reduction block (DDR, QDR or ODR) 16, a deskewer 18 and a re-timing buffer 20. Since a timing signal is not generally transmitted in the data stream to a receiver, a CDR circuit 14 is used to regenerate a bit clock from the received data stream. Since individual serial transmission lines may have different time delays (because they are of different lengths etc.), the deskewer 18 is used to re-align data transmitted in parallel over multiple serial transmission lines. Finally, a reference clock 22 is used to control the timing of the CDR circuit 14, the deserialiser 16, deskewer 18 and the re-timing buffer 20.

Data transmitted at a double data rate (DDR) undergoes a transition at every clock edge. In other words, the data undergoes a transition at a rising clock edge and a falling clock edge. In contrast, data transmitted at a single data rate (SDR) undergoes a transition at every second clock edge (i.e. on either a rising clock edge or a falling clock edge).

The goal of a receiver in a digital data transmission system is to sample a received waveform at the point where its voltage and timing margins are as large as possible in order to minimize the risk of assigning an incorrect bit value to the sample. However, the increased data rates accommodated by high-speed data buses tend to accentuate irregularities in the signal stream. Furthermore, hardware analogue effects become more evident at higher data rates. Consequently, precise signal timing becomes more critical at higher data rates. One of the key metrics for quantifying the performance of a data transmission system is bit error rate (BER).

Referring to FIG. 2, a bit error testing circuit/device 40 typically comprises generator module 42 and a receiver module 44 which are respectively connectable to a transmitter T_(x) and a receiver R_(x). The transmitter T_(x) is connected to the receiver R_(x) through data bus 46. The generator module 42 comprises a first test pattern generator LFSR_(GEN) and the receiver module 44 comprises a second test pattern generator LFSR_(REC), comparator 48 and counter 50.

In use, the first test pattern generator LFSR_(GEN) transmits a pre-defined test pattern PRBS_(GEN) to the transmitter T_(x). The transmitter T_(x) then transmits the test pattern through the data bus 46 to the receiver. R_(x). The receiver R_(x) samples the bits from the received waveform and transmits the resulting bit sequence to the comparator 48. The second test pattern generator LFSR_(REC) generates a confirmation pattern PRBS_(REC) that matches the test pattern PRBS_(GEN) generated by the first test pattern generator LFSR_(GEN). The second test pattern generator LFSR_(REC) transmits the confirmation pattern PRBS_(REC) to the comparator 48, which compares the confirmation pattern PRBS_(REC) to the bit sequence received from the receiver R_(x). The bit error rate is calculated as the number of bits that differ between the confirmation pattern PRBS_(REC) and the bit sequence sampled from the waveform received by the receiver.

A pseudo-random bit sequence (PRBS) is a widely used test pattern for assessing bit error rates (BER). A PRBS is a particularly useful test pattern as it is an algorithmically determined, predictable and repeatable bit sequence that has the same statistical characteristics as a random sequence. These statistical characteristics mean that a PRBS can be readily used to simulate live traffic on a transmission line.

A PRBS can be generated by a linear feedback shift register (LFSR), in which some of the outputs from the register are fed back to its input through an XOR logic gate. By selecting different register lengths and feedback outputs it is possible to generate different output patterns. In particular, by correctly choosing the feedback outputs from an n-bit LFSR it is possible to generate a PRBS of length 2^(n)−1, i.e. a maximal length sequence that includes all the possible permutations (patterns) of the n-bits, excluding the all-zeros pattern.

In light of the above discussion of PRBS test patterns and referring back to FIG. 2, for the sake of clarity the first test pattern generator LFSR_(GEN) will be known henceforth as the generator LFSR. In addition, the test pattern PRBS_(GEN) generated by the generator LFSR will be known henceforth as the generator PRBS. Similarly, the second test pattern generator LFSR_(REC) and confirmation pattern PRBS_(REC) generated therefrom will be respectively known henceforth as the receiver LFSR and the receiver PRBS.

PROBLEMS WITH THE PRIOR ART

One of the main problems in bit error testing is synchronizing the generator LFSR with the receiver LFSR so that the bit sequence sampled from the waveform of the test pattern PRBS_(GEN) can be validly compared with the receiver PRBS PRBS_(REC). Traditional approaches to solving this problem have been based on the detection of a specific pre-defined bit sequence (e.g. training pattern specified in SP14 standard) in the bit sequence sampled from a received waveform. However, this introduces the necessity of generating and including a specific bit sequence in the generator PRBS.

For the purposes of bit error testing the most straightforward method of guaranteeing a data transition at each clock edge of a deskewer is to run the generator LFSR at double the speed of the deskewer. However, whilst a generator LFSR is typically capable of running at this rate, a receiver LFSR with its additional bit sequence analysis circuitry is generally not.

The process of converting from SDR data to DDR or vice versa, normally involves multiplying or dividing the clock signal as appropriate. However, the use of a clock divider makes the process of bit error testing more difficult as it introduces phase delays that further complicate the synchronization problem.

SUMMARY OF THE INVENTION

The present invention is directed to the circuit, device and method as defined in the independent claims for providing a self-synchronising bit error analyser. Further embodiments of the invention are provided in the appended dependent claims.

The present invention provides a mechanism for performing bit error testing on DDR and SDR data that avoids the necessity for an additional clock divider by using two bit selector circuit components.

The present invention also provides a mechanism of synchronizing a generator LFSR and a receiver LFSR without the requirement for the generation and inclusion of a specific pre-defined bit sequence within the generator PRBS.

Finally, the present invention provides a mechanism for providing different testing regimens for assessing the performance of a point-to-point data transmission medium.

BRIEF DESCRIPTION OF THE DRAWINGS

An embodiment of the self-synchronising bit error testing circuit and two embodiments of the self-synchronising bit error testing device in accordance with the invention will now be described with reference to the accompanying drawings in which:

FIG. 1 is a block diagram of a typical receiver in a hybrid parallel-serial interface;

FIG. 2 is a block diagram of a typical bit error testing device;

FIG. 3 is a block diagram of a 64-bit self-synchronising bit error testing circuit in accordance with the invention, testing a hybrid parallel-serial high speed data bus comprising fifteen 2-bit wide data lines;

FIG. 4 is a block diagram of the components of the self-synchronising bit error testing circuit shown in FIG. 3 employed in testing the performance of a pair of the 2-bit wide data lines from the data bus shown in FIG. 3;

FIG. 5 is a DDR signal-timing diagram for the self-synchronising bit error testing circuit shown in FIG. 3;

FIG. 6 is a SDR signal-timing diagram for the self-synchronising bit error testing circuit shown in FIG. 3;

FIG. 7 is a circuit diagram of one of the LFSRs employed in the self-synchronising bit error testing circuit shown in FIG. 3;

FIG. 8 is a state diagram of the self-synchronising bit error testing circuit shown in FIG. 3;

FIG. 9 is a block diagram of a first embodiment of the self-synchronising bit error testing device comprising the self-synchronising bit error testing circuit shown in FIG. 3;

FIG. 10 is a detailed view of the fifth and sixth cells of the LFSR employed in the first embodiment of the self-synchronising bit error testing device shown in FIG. 9;

FIG. 11 is a timing diagram of the control signals and operational phases of the first embodiment of the self-synchronising bit error testing device shown in FIG. 9;

FIG. 12 is a block diagram of a second embodiment of the self-synchronising bit error testing device employing multiple generator and receiver LFSRs; and

FIG. 13 is a more detailed view of the third and fourth LFSRs (receiver or generator) of the second embodiment of the self-synchronising bit error testing device shown in FIG. 12.

DETAILED DESCRIPTION OF THE INVENTION

The following description will discuss the following topics:

(a) a self-synchronising bit error testing circuit capable of handling SDR and DDR data; and

(b) a self-synchronising bit error testing device employing the self-synchronising bit error testing circuit.

A. General Purpose Self-Synchronising Bit Error Testing Circuit

1. Hardware Architecture

(i) Overview

The self-synchronising bit error testing circuit provides a mechanism for testing the re-alignment and bit recovery function of a deskewer configured for either DDR (double data rate) or SDR (single data rate) data. The following description employs the specific example of 64-bit self-synchronising bit error testing circuit used for testing the performance of a data bus comprising thirty two data lines, wherein each data line is 2-bits wide. However, it will be appreciated that the self-synchronising bit error testing circuit is not limited to this specific example and could in fact be used to assess the integrity of data transmission through any point to point transmission medium.

Referring to FIG. 3, a transmitter T_(x) and a receiver R_(x) are connected by a data bus 100 comprising fifteen 2-bit wide data lines L(0) to L (31). For the sake of clarity, the data lines and circuit elements on the transmitter side of the data bus 100 will be henceforth designated by a ‘T’ superscript and the data lines and circuit elements on the receiver side of the data buses will be designated by a ‘R’ superscript. Communications between the transmitter T_(x), receiver R_(x) and data lines L(0) to L(31) are facilitated by multiplexers MUX^(T) 51 and MUX^(R) 52 and de-multiplexers DEMUX^(R) (54)

The generator module 142 of the self-synchronising bit error testing circuit comprises sixteen identical 12-bit LFSRs (namely LFSR_(GEN)(0) to LFSR_(GEN)(15)) operating in parallel. The receiver module 144 of the self-synchronising bit error testing circuit comprises sixteen corresponding identical 12-bit LFSRs (namely LFSR_(REC)(0) to LFSR_(REC)(15)). The receiver module 144 of the self-synchronising bit error testing circuit also comprises sixteen bit samplers (namely B/S^(R) (0) to B/S^(R)(15)) controlled by a system clock 55. For the sake of simplicity the operation of the self-synchronising bit error testing circuit will be described in terms of the testing operations on two of the 2-bit data lines (L(0) to L(31)). However, it will be realised that, in practice, the testing operations described below would be simultaneously performed on all fifteen of the 2-bit data lines.

Take for example the generator LFSR LFSR_(GEN(0)). in use, the generator LFSR LFSR_(GEN(0)) transmits four bits from a PRBS onto data lines L^(T)(0) to L^(T)(3). The four bits are then transmitted to a 2:1 multiplexer MUX^(T) and formed into bit pairs. The bit pairs are then loaded onto each of the 2-bit wide lines L(0) and L(1). T_(x)e two bit pairs are transmitted to bit recovery circuits (not shown) and a receiver multiplexer MUX^(R) (52). The receiver multiplexers MUX^(R) operate at a 2:1 rate for high-speed data and 4:1 for low speed data (in which case the data are not multiplexed by MUX^(T) block 51).

The data from the receiver multiplexer MUX^(R) 52 are transmitted to a deskewer core device (SPI4) 53 that re-aligns the data streams received from each of the receiver multiplexer MUX^(R) associated with each of the data lines L(0) to L(31). The re-aligned data from the first two data lines (L(0) and L(1)) are transmitted to a 1:4 demultiplexer DEMUX^(R) and the four resulting bits are then transmitted along data lines L^(R)(0) to L^(R)(3) to the bit sampler B/S^(R)(0).

Every two cycles of the system clock 55, the bit selector B/S^(R(0)) selects four bits from data line L(0,1) and transmits it to the receiver LFSR LFSR_(REC(0)) for use in testing the synchronisation of the generator LFSR and the receiver LFSR. Otherwise, the data from the bit selector B/S^(R(0)) are transmitted directly to a comparator (not shown) for use in determining the bit error rate of the data line (L(0,1)) in accordance with the previously described traditional methods of bit error testing.

FIG. 4 shows the components of the self-synchronising bit error testing circuit employed in testing the pair of data lines L(0) and L(1) in more detail. In particular, the receiver module 144 comprises a switch 56, which switches the output of the bit selector B/S^(R)(0) to the receiver LFSR LFSR_(REC) to thereby load the receiver LFSR LFSR_(REC) at the start of the synchronisation procedure. Thereafter, the switch 56 switches the output of the bit selector B/S^(R)(0) to the comparator COMPAR(0) that compares the four bits received from the bit selector B/S^(R)(0) with four bits from the output of the receiver LFSR LFSR_(REC).

The phase of the receiver LFSR LFSR_(REC) is altered in accordance with the feedback loop F_BACK(0). If the receiver LFSR LFSR_(REC) is not synchronised with the generator LFSR_(GEN), a new synchronisation is tried by selecting another four bits from the bit selector B/S^(R)(0) under the control of control loop CTRL_LOOP(0). The process is repeated until a synchronisation is verified fifteen times. Only four trials at maximum are required to select the correct four bits.

(ii) Signal Timing

The timing of the signals (SDR and DDR) transmitted in the self-synchronizing bit error testing circuit are shown more clearly in FIGS. 5 and 6 in which traces A-D show the generator LFSR control and output signals; traces E-L show the receiver LFSR control and output signals; and traces M-P show the main deskew core signals.

More particularly:

Generator LFSR Control and Output Signals

Trace A: shows the generator LFSR clock running at half the speed of the deskew core;

Trace B: shows the the SDR/DDR control signals for the transmitter T_(x);

Trace C: shows a 4-bit selection from the generator PRBS PRBS_(GEN); and

Trace D: shows the 12-bits of the generator LFSR LFSR_(GEN) register (in hexadecimal format).

Receiver LFSR Control and Output Signals

Trace E: shows 4-bits of data sampled from the generator PRBS;

Trace F: shows the SDR/DDR control signals for the receiver R_(x);

Trace G: shows the check state;

Trace H: shows the 12-bits of the receiver LFSR LFSR_(REC) register (in hexadecimal format);

Trace I: shows the receiver 4-bit counter (in hexadecimal format);

Trace J: shows a bit selector incrementer (in unsigned format);

Trace K: shows the latched data in the data bus (in hexadecimal format);and

Trace L: shows the selected nibble received by the receiver LFSR (in hexadecimal format).

Main Deskew Core Signals

Trace M: shows the 16 bit data bus (in hexadecimal format);

Trace N: shows the data (in hexadecimal format) on the data bus comprising thirty two 2-bit wide data lines;

Trace O: shows the entire data-set transmitted through the 64-bit self-synchronizing bit error testing circuit (in hexadecimal format); and

Trace P: shows the deskew core system clock.

It should be noted that when the data bus and self-synchronizing bit error testing circuit are operating at high speed, the data to be tested are transmitted at twice the speed of the generator and receiver LFSRs. Consequently, only the first 32 low bits from the data bus are used and the remaining 32 bits are set at zero.

When operating at a low speed the data to be tested are transmitted at the same speed as the receiver and generator LFSRs. Accordingly, the data to be tested is not multiplexed and the entire capacity of the bus (i.e. the entire 64 bits) is used.

(iii) LFSR Configuration

The same 12-bit LFSR circuit is employed in the generator module and the receiver module of the self-synchronizing bit error testing circuit. The LFSR was chosen to be 12 bits in length to ensure that enough patterns were generated to enable both SDR and DDR data to be analysed. In particular, a 12-bit LFSR generates 4095 pseudo-random patterns. FIG. 7 shows the LFSR employed in the generator and receiver modules of the self-synchronising bit error tester and the mechanism by which the generator/receiver LFSR handles SDR and DDR data.

The bottom of FIG. 7 shows all the cells (C₀₋C₁₁) of the 12-bit LFSR. A switch DC₀ is provided between cells C₁ and C₂ and a further switch DC₁ is provided between cells C₇ and C₈.

As previously discussed, when synchronizing a receiver LFSR with a generator LFSR, a 4-bit selection is made from output of the deskwer in the receiver R_(x). These four bits are shown at the top of FIG. 7 as bits B(0) to B(3) and are connected to the LFSR cells by selectors S₀ to S₄.

Normally a 12-bit LFSR has a ‘tap’ at cells C₀, C₃, C₅ and C₁₁. However, in order to avoid loading a zero value into the LFSR, the tap at cell C₁₁ is skipped and an XOR is introduced only at cells C₀, C₃ and C₅ (shown as X₀, X₃ and X₅ respectively). The output from cell C₁₁ is employed in a feedback structure to cells C₀, C₁ (through XOR gate X₀), C₄ (through XOR gate X₁) and C₆ (through XOR gate X₂).

The one-to-many feedback structure enables the LFSR to operate at a higher clock speed than a ‘many-to-one’ feedback structure.

2. Operation

FIG. 8 shows the operation of the self-synchronizing bit error testing circuit in more detail. In a first step (RESET 66) the receiver LFSR is reset. In the next step (LOAD 68), the receiver LFSR is loaded with the data received from the generator LFSR.

Returning for a moment to FIG. 7, when loading data into the receiver LFSR, the feedback signal to the LFSR cells is not the output from cell C₁₁. Instead, the LFSR feedback is the input data bit B(3).

When receiving DDR data, the switches DC₀ and DC₁ are maintained in an open state and data from the receiver deskewer is loaded into the LFSR via the selectors at cells C₀, C₁, C₂, C₄, C₆ and C₈. A further XOR logic gate (namely X₃) is provided at the input to LFSR cell C₄. Consequently, the input to cell C₄ is bit B(3) XOR bit B(1).

As will be recalled, the same LFSR is employed for SDR and DDR data. For SDR data only two bits from the 4-bit selection from the receiver deskewer are loaded into the LFSR. In particular, bits B(0) and B(2) are not loaded into the LFSR. This is achieved by closing switches DC₀ and DC₁ so that cell C₁ is directly connected to cell C₂ and cell C₇ is directly connected to cell C₈. This enables the input to cells C₂ and C₈ to bypass selectors S₂ and S₄ respectively.

By choosing adequately separated bits (bits 1, 3, 7 and 11) instead of consecutive bits from an LFSR it is possible to run the LFSR at half the speed of the deskewer and still have DDR (double data rate) data at the input and/or output of the deskewer. Furthermore it is possible to create SDR data by taking only two bits from the LFSR and repeating them (bits 3, 3, 11 and 11) with no clock division.

Returning to FIG. 8, once data is loaded into the receiver LFSR, the self-synchronizing bit error testing circuit performs a TEST step 70 (if the COMPARE is successful) in which a confirmation pattern is generated by the receiver LFSR by switching its multiplexers into feedback mode and inserting taps (at cells C₀, C₃ and C₅) into the feedback line. The confirmation pattern is then compared against the generator PRBS pattern received by the receiver.

If the confirmation pattern does not match the received generator PRBS pattern, the self-synchronizing bit error testing circuit returns to the LOAD step 68 and loads a further 4-bit selection from the generator PRBS pattern into the receiver LFSR. The TEST step 70 is repeated using the updated 4-bit selection.

The LOAD step 68 and TEST step 70 are repeated until a phase lock is achieved between the confirmation pattern and the received generator PRBS pattern. With each cycle of the LOAD 68 and TEST 70 operations a counter CTR_(A) is incremented CTR_(A)++72.

If a match is not achieved between the confirmation pattern and the received generator PRBS within 16 cycles of the LOAD 68/TEST 70 operations (CTR_(A)=16, 74), the input data is shifted by one position to the right (B/S>>76), a bit shift counter is incremented (SHFT++78) and the LOAD 68/TEST 70 operations are repeated until a match is detected between a received generator PRBS pattern and a confirmation PRBS pattern.

Once a valid phase lock has been achieved (i.e. a match is achieved between a confirmation PRBS pattern and a received generator PRBS pattern) a check is performed to ensure that the output from the receiver LFSR does not solely comprise zeros (ZEROS 82) (i.e. there is no data in the input data stream). If the receiver LFSR output does solely comprise zeros, the state machine returns to the LOAD state 68.

If a valid phase lock has been achieved and the output from the receiver LFSR does not solely comprise zeros, a further counter is incremented (Ctr_(B)++84) (noting of course that CTR_(B) may equal CTR_(A)). In particular, the phase lock must be validated fifteen times to ensure the correct synchronisation of the generator and receiver LFSRs. If the phase lock has been validated fifteen times (CTR_(B)=15, 86) the receiver and generator LFSRs are deemed to be synchronized and the relative timing of the receiver and generator LFSRs is locked (i.e. LOCK state 88). Once the locked state (LOCK 88) has been attained, it can only be left by a reset (RESET 66).

When the self-synchronizing bit error testing circuit has attained the locked state the generator LFSR and the receiver LFSR are allowed to run continuously. At each cycle the generator PRBS is compared to the receiver PRBS. When an error is detected, a counter (not shown) is incremented which allows a bit error rate (BER 90) to be computed in accordance with the traditional methods of BER testing. The VHDL code for the BER testing operations is shown below:

checking_ok <= ‘1’ WHEN LFSR_Reg(11) & LFSR_Reg(7) & LFSR_Reg(3) & LFSR_Reg(1) = selectedbyte ELSE ‘0’;

The VHDL code for performing the above-described synchronization process by the bit selector is shown below. Since a data transition can start anywhere within the 4-bit selection loaded into the receiver LFSR, a small two-stage buffer composed of the input data bus and the latched data bus (datain_del bus) is used to make a new estimate of the position of crossing over points in the received data stream every 16 cycles (i.e. when the bit selector is changed) until a match is found between the selected digits and the data generated by the receiver LFSR. For instance at the start of a received waveform, with a bit selector at 3, dat=x‘1’ and datain_del=x ‘E’, the selected byte (in fact digit) is equal to x‘C’.

sel_c: PROCESS (dat, datain_del, bitselector, lfsr_reg) BEGIN IF (sdr = ‘0’) THEN /* Double data rate, all the bus is taken as is */ CASE bitselector IS WHEN “00” => selectedbyte <= dat; WHEN “01” => selectedbyte <= datain_del(0) & dat(3 DOWNTO 1); WHEN “10” => selectedbyte <= datain_del(1 DOWNTO 0) & dat(3 DOWNTO 2); WHEN “11” => selectedbyte <= datain_del(2 DOWNTO 0) & dat(3); WHEN OTHERS => NULL; END CASE; ELSE /* Single data rate, only 2 bits are taken, */ /* and the others are taken from the LFSR */ CASE bitselector IS WHEN “00” => selectedbyte <= dat(3) & lfsr_reg(7) & dat(1) & lfsr_reg(1); WHEN “01” => selectedbyte <= datain_del(0) & lfsr_reg(7) & dat(2) & lfsr_reg(1); WHEN “10” => selectedbyte <= datain_del(1) & lfsr_reg(7) & dat(3) & lfsr_reg(1); WHEN “11” => selectedbyte <= datain_del(2) & lfsr_reg(7) & datain_del(0) & lfsr_reg(1); WHEN OTHERS => NULL; END CASE;

B. Self-Synchronising Bit Error Testing Device Employing the Self-Synchronising Bit Error Testing Circuit

1. Circuit Hardware Architecture

FIG. 9 shows a 9-bit LFSR circuit for use in the bit error testing device, in which the outputs from cells C₅ and C₇ are employed in the feedback loop to latch C₀. However, it will be appreciated that the invention is not limited to this specific example and could instead embrace LFSRs of other lengths with different feedback connections.

If the data bus is a 9 bit BUS (for instance 1 byte and its parity), then a simple schematic to load the receiver LFSR would be to load all bits of the data bus. In this case no bit selector and no finite state machine with the LOAD, VALID, LOCK states is needed but the generator and receiver LFSRs must run at the same speed as the device under test.

The operation of the bit error testing devices will be described in more detail with reference to the operations of one of the cells (e.g. cell C₅) shown in FIG. 9. To this end, FIG. 10 shows a more detailed view of the circuit components between cell C₄ and cell C₅.

The input multiplexer MUX between cells C₄ and C₅ comprise a network of AND and OR logic gates arranged to multiplex the output from cell C₄ (i.e. Q4) with the sixth bit B(5) received from the data bus connecting the receiver and transmitter.

The sixth bit B(5) is also transmitted to a D-type flip-flop 92 the output (D5rec) of which is transmitted to comparator 248. The comparator 248 compares D5rec with the output Q₅ of cell C₅. The results of this comparison are combined with a control signal TEST_START_(b) by way of a NOR logic gate 94 to produce an error signal Err_Sig that is used to control the operation of an error management circuit ERR_CIRC.

2. Operational Phases

In use, the circuit operates in two phases, namely a no test phase and a verification phase. Both of these operational phases will be described in more detail below by referring to FIG. 10 together with the signals shown in FIG. 11.

Phase 1: No test (Time Period T₀ to T₁)

Before the TEST_STARTb signal becomes active all the data coming from the receiver are latched into the register at the same time.

Consequently, when the output Q₅ from cell C₅ is compared with the D5rec signal both of the signals have the same value.

Phase 2: Verification

When the TEST_START_(b) signal becomes active, the cells C₀ to C₈ are connected in series. On the next clock cycle the output Q5 of the cell C₅ is compared to the output D5rec of the flip-flop 92, which is equal to the sixth bit B(5).

Since the generator LFSR and the receiver LFSR are now operating independently of each other the synchronization made at time T₁ enables the detection of any differences between the outputs of the LFSRs that indicates lost data.

3. Error Management Circuit (ERR_CIRC)

The error management circuit receives an error signal from the comparator 248 and is used for correcting a single bit error occurring along the length of the receiver LFSR. The error management circuit also enables the receiver LFSR to be stopped and restarted on detection of a bit error so that the bit error can be loaded in a counter and the BER incremented.

C. Multiple LFSR Self-Synchronizing Bit Error Testing Device

1. Hardware Architecture

The generator module and the receiver module in the above-described bit error testing device include a single generator LFSR and a single receiver LFSR respectively. However, the bit error testing functionality of the bit error testing device can be enhanced by the generation of multiple test patterns to provide a more comprehensive testing regime. In particular, referring to FIG. 12, a generator module includes a PRBS generator comprised of several LFSRs of different configuration and length. In a given verification phase, any one of the LFSRs may be selected by a multiplexor MUX. In the event that a generator module contains only a single LFSR, the configuration of the LFSR may be altered by changing its XOR connections.

In the case of a generator module containing multiple LFSRs, the receiver module must also include several LFSRs operating in parallel to ensure that at least one of the receiver LFSRs matches the generator LFSR.

2. Operation

As in the previously described single LFSR bit error testing device, the multiple LFSR bit error testing device has two operational phases, namely the No test phase and the verification phase. Both of these operational phases will be described in more detail below by referring to FIG. 12 together with the signal timing diagram in FIG. 11.

Phase 1: No Test Phase

During the No Test Phase (i.e. before the TEST-STARTb control signal becomes active), no error checking is effectively performed since all the generator and receiver LFSRs are loaded with the same value in accordance with the data present on the data bus.

Phase 2: Verification Phase

At time T₁ the control signal TEST_STARTb becomes active and all the LFSRs are isolated from the value on the data bus and start to run in LFSR mode. Each LFSR has an additional register PM (pattern matching) that is set to one at time T₁. The output of the PM register returns to zero if there is a mismatch between the transmitted generator PRBS and the receiver PRBS. If after a few clock cycles any one of the PM registers contains a ‘1’ value the corresponding receiver LFSR is deemed to match the generator LFSR and BER determination becomes possible. However, in the event that one the PM registers contain a ‘0’ value a failure is deemed to have occurred and the system is reset.

It will be recognized that it is possible to use different transmitter LFSRs during different test cycles T_(i) to T_(i+1) (i>1) and thereby provide comprehensive testing on the fly.

Whilst the discussions so far have focussed on the use of the self-synchronising bit error testing circuit and device for testing computer data buses, it will be appreciated that the self-synchronising bit error-testing device could be used, with minor modifications, to assess the performance of any point-to-point digital transmission medium.

Modifications and alterations may be made to the above without departing from the scope of the invention. 

1. A method of synchronising a generator LFSR and a receiver LFSR in a data bus analyser comprising the steps of: (a) selecting a sample of data generated by the generator LFSR; (b) transmitting the sample through a data bus; (c) selecting a sample of data generated by the receiver LFSR; (d) comparing the sample of data from the generator LFSR with the sample of data from the receiver LFSR; (e) adjusting the receiver LFSR based on step (d); and (f) repeating steps (a) to (e) until the sample of data from the receiver LFSR is substantially the same as the sample of data from the generator LFSR.
 2. The method of synchronising a generator LFSR and a receiver LFSR in a data bus analyser as claimed in claim 1 wherein the step (e) of adjusting the receiver LFSR comprises right shifting the receiver LFSR.
 3. The method of synchronising a generator LFSR and a receiver LFSR in a data bus analyser as claimed in claim 1 wherein the method is preceded by a step of initialising the receiver LFSR with a sample of data generated by the generator LFSR.
 4. The method of synchronising a generator LFSR and a receiver LFSR in a data bus analyser as claimed in claim 1 wherein step (f) is a followed by a verification procedure in the event that the sample of data from the receiver LFSR substantially matches the sample of data from generator LFSR and wherein the verification procedure comprises the steps of: (g) selecting a further sample of data generated by the generator LFSR; (h) transmitting the further sample through the data bus; (i) selecting a further sample of data generated by the receiver LFSR; (j) comparing the further sample of data generated by the generator LFSR with the further sample of data generated by the receiver LFSR; and (k) restarting steps (a) to (f) of the method of synchronising the generator LFSR with the receiver LFSR in the event that the further sample of data from the receiver LFSR does not substantially match the further sample of data from the generator LFSR. 